In previous posts, we had discussed equalization of a 2×2 MIMO channel with Zero Forcing (**ZF**) equalization and later, Zero Forcing equalization with successive interference cancellation (**ZF-SIC**). In this post, we will explore a variant of **ZF-SIC** called **Zero Forcing Successive Interference Cancellation with optimal ordering**. We will assume that the channel is a flat fading Rayleigh multipath channel and the modulation is BPSK.

Brief description of 2×2 MIMO transmission, assumptions on channel model and the noise are detailed in the post on Zero Forcing equalization with successive interference cancellation

## Zero forcing equalizer for 2×2 MIMO channel

Let us now try to understand the math for extracting the two symbols which interfered with each other. In the first time slot, the received signal on the first receive antenna is,

.

The received signal on the second receive antenna is,

.

where

, are the received symbol on the first and second antenna respectively,

is the channel from transmit antenna to receive antenna,

is the channel from transmit antenna to receive antenna,

is the channel from transmit antenna to receive antenna,

is the channel from transmit antenna to receive antenna,

, are the transmitted symbols and

is the noise on receive antennas.

For convenience, the above equation can be represented in matrix notation as follows:

.

Equivalently,

To solve for , The **Zero Forcing (ZF) linear detector** for meeting this constraint . is given by,

.

Using the **Zero Forcing (ZF)** equalization, the receiver can obtain an estimate of the two transmitted symbols , , i.e.

.

## Successive Interference Cancellation with optimal ordering

In classical **Successive Interference Cancellation**, the receiver arbitrarily takes one of the estimated symbols, and subtract its effect from the received symbol and . However, we can have more intelligence in choosing whether we should subtract the effect of first or first. To make that decision, let us find out the transmit symbol (after multiplication with the channel) which came at higher power at the receiver. The received power at the both the antennas corresponding to the transmitted symbol is,

.

The received power at the both the antennas corresponding to the transmitted symbol is,

.

**If then the receiver decides to remove the effect of from the received vector and **** and then re-estimate .**

.

Expressing in matrix notation,

,

Optimal way of combining the information from multiple copies of the received symbols in receive diversity case is to apply **Maximal Ratio Combining (MRC)**. The equalized symbol is,

.

**Else if **** the receiver decides to subtract effect of from the received vector and , and then re-estimate **

.

Expressing in matrix notation,

,

Optimal way of combining the information from multiple copies of the received symbols in receive diversity case is to apply **Maximal Ratio Combining (MRC)**. The equalized symbol is,

.

Doing **successive interference cancellation with optimal ordering** ensures that the reliability of the symbol which is decoded first is guaranteed to have a lower error probability than the other symbol. This results in lowering the chances of incorrect decisions resulting in erroneous interference cancellation. Hence gives lower error rate than simple successive interference cancellation.

## Simulation Model

The Matlab/Octave script performs the following

(a) Generate random binary sequence of +1’s and -1’s.

(b) Group them into pair of two symbols and send two symbols in one time slot

(c) Multiply the symbols with the channel and then add white Gaussian noise.

(d) Equalize the received symbols with Zero Forcing criterion

(e) Find the power of received symbol from both the spatial dimensions.

(f) Take the symbol having higher power, subtract from the received symbol

(f) Perform Maximal Ratio Combining for equalizing the new received symbol

(g) Perform hard decision decoding and count the bit errors

(h) Repeat for multiple values of and plot the simulation and theoretical results.

Click here to download Matlab/Octave script for computing BER for 2×2 MIMO channel equalized by ZF-SIC with optimal ordering

**Figure: BER plot for BPSK in 2×2 MIMO equalized by ZF-SIC with optimal ordering**

## Observations

Compared to Zero Forcing equalization with successive interference cancellation case, addition of optimal ordering results in around 2.0dB of improvement for BER of .

## References

[DIG-COMM-BARRY-LEE-MESSERSCHMITT] Digital Communication: Third Edition, by John R. Barry, Edward A. Lee, David G. Messerschmitt

%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%% % All rights reserved by Krishna Pillai, http://www.dsplog.com % The file may not be re-distributed without explicit authorization % from Krishna Pillai. % Checked for proper operation with Octave Version 3.0.0 % Author : Krishna Pillai % Email : krishna@dsplog.com % Version : 1.0 % Date : 09 Novemeber 2008 % %%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%%% % Script for computing the BER for BPSK modulation in a % Rayleigh fading channel with 2 Tx, 2Rx MIMO channel % Zero Forcing Equalization with Successive Interference % Cancellation (ZF-SIC) with optimal ordering clear N = 10^6; % number of bits or symbols Eb_N0_dB = [0:25]; % multiple Eb/N0 values nTx = 2; nRx = 2; for ii = 1:length(Eb_N0_dB) % Transmitter ip = rand(1,N)>0.5; % generating 0,1 with equal probability s = 2*ip-1; % BPSK modulation 0 -> -1; 1 -> 0 sMod = kron(s,ones(nRx,1)); % sMod = reshape(sMod,[nRx,nTx,N/nTx]); % grouping in [nRx,nTx,N/NTx ] matrix h = 1/sqrt(2)*[randn(nRx,nTx,N/nTx) + j*randn(nRx,nTx,N/nTx)]; % Rayleigh channel n = 1/sqrt(2)*[randn(nRx,N/nTx) + j*randn(nRx,N/nTx)]; % white gaussian noise, 0dB variance % Channel and noise Noise addition y = squeeze(sum(h.*sMod,2)) + 10^(-Eb_N0_dB(ii)/20)*n; % Receiver % ---------- % Forming the ZF equalization matrix W = inv(H^H*H)*H^H % H^H*H is of dimension [nTx x nTx]. In this case [2 x 2] % Inverse of a [2x2] matrix [a b; c d] = 1/(ad-bc)[d -b;-c a] hCof = zeros(2,2,N/nTx) ; hCof(1,1,:) = sum(h(:,2,:).*conj(h(:,2,:)),1) ; % d term hCof(2,2,:) = sum(h(:,1,:).*conj(h(:,1,:)),1) ; % a term hCof(2,1,:) = -sum(h(:,2,:).*conj(h(:,1,:)),1); % c term hCof(1,2,:) = -sum(h(:,1,:).*conj(h(:,2,:)),1); % b term % Sorting the equalization matrix based on the channel power on each dimension % since the second spatial dimension is equalized first, the channel % with higher power assigned to second dimension normSS1 = squeeze(hCof(2,2,:)); normSS2 = squeeze(hCof(1,1,:)); sortIdx = find(normSS2 < normSS1); % sorting the H^H*H matrix hCofSort = hCof; hCofSort(2,2,sortIdx) = hCof(1,1,sortIdx); hCofSort(1,1,sortIdx) = hCof(2,2,sortIdx); hCofSort(1,2,sortIdx) = hCof(2,1,sortIdx); hCofSort(2,1,sortIdx) = hCof(1,2,sortIdx); hDen = ((hCofSort(1,1,:).*hCofSort(2,2,:)) - (hCofSort(1,2,:).*hCofSort(2,1,:))); % ad-bc term hDen = reshape(kron(reshape(hDen,1,N/nTx),ones(2,2)),2,2,N/nTx); % formatting for division hInvSort = hCofSort./hDen; % inv(H^H*H) % sorting the H matrix hSort = h; hSort(:,2,sortIdx) = h(:,1,sortIdx); hSort(:,1,sortIdx) = h(:,2,sortIdx); % Equalization - Zero forcing hModSort = reshape(conj(hSort),nRx,N); % H^H operation yModSort = kron(y,ones(1,2)); % formatting the received symbol for equalization yModSort = sum(hModSort.*yModSort,1); % H^H * y yModSort = kron(reshape(yModSort,2,N/nTx),ones(1,2)); % formatting yHatSort = sum(reshape(hInvSort,2,N).*yModSort,1); % inv(H^H*H)*H^H*y % receiver - hard decision decoding on second spatial dimension ipHat2SS = real(yHatSort(2:2:end))>0; ipHatMod2SS = 2*ipHat2SS-1; ipHatMod2SS = kron(ipHatMod2SS,ones(nRx,1)); ipHatMod2SS = reshape(ipHatMod2SS,[nRx,1,N/nTx]); % new received symbol - removing the effect from second spatial dimension h2SS = hSort(:,2,:); % channel in the second spatial dimension r = y - squeeze(h2SS.*ipHatMod2SS); % maximal ratio combining - for symbol in the first spatial dimension h1SS = squeeze(hSort(:,1,:)); yHat1SS = sum(conj(h1SS).*r,1)./sum(h1SS.*conj(h1SS),1); yHatSort(1:2:end) = yHat1SS; yHatSort = reshape(yHatSort,2,N/2) ; yHatSort(:,sortIdx) = flipud(yHatSort(:,sortIdx)); yHat = reshape(yHatSort,1,N); % receiver - hard decision decoding ipHat = real(yHat)>0; % counting the errors nErr(ii) = size(find([ip- ipHat]),2); end simBer = nErr/N; % simulated ber EbN0Lin = 10.^(Eb_N0_dB/10); theoryBer_nRx1 = 0.5.*(1-1*(1+1./EbN0Lin).^(-0.5)); p = 1/2 - 1/2*(1+1./EbN0Lin).^(-1/2); theoryBerMRC_nRx2 = p.^2.*(1+2*(1-p)); close all figure semilogy(Eb_N0_dB,theoryBer_nRx1,'bp-','LineWidth',2); hold on semilogy(Eb_N0_dB,theoryBerMRC_nRx2,'kd-','LineWidth',2); semilogy(Eb_N0_dB,simBer,'mo-','LineWidth',2); axis([0 25 10^-5 0.5]) grid on legend('theory (nTx=2,nRx=2, ZF)', 'theory (nTx=1,nRx=2, MRC)', 'sim (nTx=2, nRx=2, ZF-SIC-Sort)'); xlabel('Average Eb/No,dB'); ylabel('Bit Error Rate'); title('BER for BPSK modulation with 2x2 MIMO and ZF-SIC-Sorted equalizer (Rayleigh channel)');

2019年6月03日 18:54

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